Method and apparatus for automatic reduction of noise in signals transmitted over conductors

ABSTRACT

A method and apparatus for automatic reduction of noise in video signals transmitted over conductors is presented. The present invention provides an adjustable amount of noise filtering matched to the amount of gain provided by an adjustable gain amplifier to a received video signal. One or more stages of a multi-stage discrete gain amplifier is provided with a corresponding noise filter circuit. The filter circuit is matched to the frequency response of and the amount of gain provided by the discrete gain amplifier stage. When the amplifier stage is applied to the received signal, the corresponding noise filter for that stage is invoked as well. In that manner, the amount of noise filtering applied to a video signal automatically varies with the amount of amplification provided to that signal.

CROSS-REFERENCE TO RELATED APPLICATION

This patent application is a continuation of U.S. patent applicationSer. No. 11/309,123 entitled “Method and Apparatus for AutomaticReduction of Noise in Video Transmitted over Conductors” filed on Jun.21, 2006, the specification, claims and abstract of which areincorporated by reference in their entirety herein.

FIELD OF THE INVENTION

This invention relates to the field of video transmission. Morespecifically the invention relates to automatic noise reduction in videosignals transmitted over conductors, including twisted pair conductors.

BACKGROUND OF THE INVENTION

Conductors (i.e. cables) are one method commonly used to conveyelectronic video signals from a source device (e.g., a video camera or aDVD player) to a destination device (e.g., a video display screen). Twotypes of cable commonly used for video transmission are coaxial cableand twisted pair cable. It is desirable for the video signal at thedestination device to correspond accurately to the original video signaltransmitted by the source device. “Insertion loss” is a term used todescribe signal degradation that occurs when a video or other signal istransmitted over a transmission medium such as a cable.

Typically, insertion loss is a function of the cable length: longerlength transmission cables will exhibit greater loss than shorter lengthcables. Coaxial cables typically exhibit less insertion loss thantwisted pair cables. However, coaxial cables are more expensive anddifficult to install than twisted pair cables. Twisted pair cablestypically are manufactured as bundles of several twisted pairs. Forexample, a common form of twisted pair cable known as “Category 5” or“CAT5” cable comprises four separate twisted pairs encased in a singlecable. CAT5 cable is typically terminated with an eight-pin RJ45connector.

Insertion loss is typically caused by the physical characteristics ofthe transmission cable. Insertion loss includes resistive losses (alsosometimes referred to as DC losses) as well as inductive, capacitive andskin effect losses (also sometimes referred to as AC losses). The ACinsertion loss exhibited by a cable is frequency dependent. For example,the insertion loss for a 1500 foot length of CAT5 cable as a function offrequency is shown in FIG. 11. In the example of FIG. 11, the insertionloss generally increases with increasing frequency, with the insertionloss for high frequency signals being significantly greater (−70 dB at50 MHz) than the DC insertion loss (−2.6 dB at 0 Hz).

Video transmitter/receiver systems exist that amplify video signalstransmitted over twisted-pair cables. In such systems, a transmitteramplifies the video source signal prior to being transmitted overtwisted pair cable, and a receiver amplifies the received signal. Thesetransmitter/receiver systems allow longer transmission distances overtwisted-pair cable than are possible for unamplified signals. However,to prevent signal distortion, the amount of gain (amplification)supplied by the transmitter and receiver must be properly matched to theamount of insertion loss that occurs in the length of the twisted-paircable over which the video signal is transmitted. If the gain applied istoo high, clipping will occur. If the gain is too low, low-levelportions of the original input signal may be lost. Ideally the systemgain should be flat across the frequency spectrum. High frequency lossresults in smearing and loss of focus in the video.

Depending on the length of cable over which the signal is transmitted,the amount of amplification required to compensate for insertion lossesmay be substantial. When substantial amplification is provided to asignal, noise becomes an issue. There exists a need for a videotransmission system that automatically compensates for noise incidentwith the amplification of video signals transmitted over appreciabledistances via conductors, including twisted pair cables.

SUMMARY OF THE INVENTION

The invention comprises a method and apparatus for automatic reductionof noise caused by amplification of video signals transmitted overappreciable distances over conductors. The present invention isparticularly applicable to noise associated with the transmission ofvideo over long lengths of CAT-5 or similar twisted-pair cables.Embodiments of the invention may be implemented as a separate deviceand/or as part of a video transmission system.

In one or more embodiments, the amount of amplification applied to areceived signal is determined from a reference signal having a knownform and strength (e.g. a pulse signal) that is provided to each pair ofconductors carrying a component of a video signal from a transmitter toa receiver. The receiver includes adjustable gain amplifiers for eachconductor pair over which a component of the video signal istransmitted. In one or more embodiments, an adjustable gain amplifiercomprises a variable gain amplifier that provides variable gain over aparticular range and a series of discrete gain amplifier stages each ofwhich provides approximately the maximum amount of gain provided by thevariable gain amplifier. The total amplifier gains are adjusted (byselecting the appropriate number of discrete gain amplifier stages plusthe appropriate amount of variable gain) such that the level of thereference signal is restored approximately to its original value.

In one or more embodiments, the present invention provides an adjustableamount of noise filtering matched to the amount of gain provided by anadjustable gain amplifier to a received video signal. In one or moreembodiments, each stage of a multi-stage discrete gain amplifier isprovided with a corresponding noise filter circuit. The filter circuitis matched to the frequency response of and the amount of gain providedby the discrete gain amplifier stage. When the amplifier stage isapplied to the received signal, the corresponding noise filter for thatstage is invoked as well. In that manner, the amount of noise filteringapplied to a video signal automatically varies with the amount ofamplification provided to that signal.

Further objects, features, and advantages of the present invention overthe prior art will become apparent from the detailed description of thedrawings that follows, when considered with the attached figures.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is an illustration of long distance twisted pair transmissionapparatus that may be used with an embodiment of the present invention.

FIG. 2 is an illustration of allocation of the conductors of twistedpair cable 106 for video signals as may be used with an embodiment ofthe present invention.

FIG. 3 is an illustration of allocation of the conductors of twistedpair cable 106 for video signals as may be used with an embodiment ofthe present invention.

FIG. 4 is a block diagram illustration of architecture of an embodimenttransmitter 104 of the apparatus of FIG. 1.

FIG. 5 is an illustration of a polarity converter in accordance with anembodiment of transmitter 104.

FIG. 6 is a block diagram illustration of architecture of receiver 108of the apparatus of FIG. 1.

FIG. 7 is an illustration of a sync stripper circuit in accordance withan embodiment of receiver 108.

FIG. 8 is an illustration of a compensation circuit in an embodiment ofreceiver 108.

FIG. 9A is an illustration of a variable compensation circuit that maybe used with an embodiment of the present invention.

FIG. 9B is an illustration of a fixed compensation circuit that may beused with an embodiment of the present invention.

FIG. 10 is an illustration of a noise filtering circuit in accordancewith an embodiment of the present invention.

FIG. 11 is a frequency response plot of an example 1500 foot long lengthof CAT5 cable.

FIG. 12 is an illustration of an elliptical filter in accordance with anembodiment of the present invention.

DETAILED DESCRIPTION OF THE INVENTION

The invention comprises a method and apparatus for automaticallyproviding of an adjustable amount of noise filtering to video signalstransmitted over conductors, such as twisted pair cable. In thefollowing description, numerous specific details are set forth toprovide a thorough description of the invention. It will be apparent,however, to one skilled in the art, that the invention may be practicedwithout these specific details. In other instances, well-known featureshave not been described in detail so as not to obscure the invention.Further, although example embodiments of the present invention aredescribed using RGBHV as an example video input signal format and CAT5cable as an example conductor over which the video signal istransmitted, it will be clear to those of skill in the art that theinvention is not limited to RGBHV and CAT5 cable and other video formatsand other cable types may be used.

In one or more embodiments, the invention is used in conjunction with atransmitter and a receiver system that enables communication of videosignals, e.g. composite video, S-Video, computer-video, and other highresolution video, over extended distances of conductors, including, forexample CAT 5 or similar twisted-pair cables. An example of such asystem is described with respect to FIGS. 1-12 below.

An embodiment of a video transmission system with which the presentinvention is used is illustrated in FIG. 1. The video transmissionsystem of FIG. 1 comprises video source 102, cable 103, transmitter 104;twisted pair cable 106; receiver 108, cable 109 and destination device110. Cable 103 couples the video (and audio, if applicable) signals fromsource 102 to transmitter 104. Cable 103 may comprise any suitableconductors known in the art for coupling the type of video signalgenerated by video source 102 to transmitter 104. Transmitter 104comprises multiple input terminals for accepting different input signalformats. For example, transmitter 104 may comprise connectors foraccepting a composite video signal, an S-Video signal, a digital videosignal, an RGB component video signal, etc. Transmitter 104 may alsocomprise standard audio connectors such as, for example RCA input jacks.

In one or more embodiments, cable 106 comprises a cable comprising abundle of multiple twisted pair conductors. For example, cable 106 maycomprise a CAT5 or similar cable comprising four pairs of twistedconductors and terminated with standard male RJ-45 connectors that matewith matching female RJ-45 connectors on the transmitter and receiver,respectively. The pairs of twisted conductors may, for example, beallocated as shown in FIGS. 2 and 3.

FIG. 4 is a block diagram showing the architecture of transmitter 104 ofFIG. 1 in an embodiment of the present invention. In the embodimentshown in FIG. 4, transmitter 104 receives a video source signalcomprising separate video input signals and sync input signals. Forexample, if the video input source signal is in RGBHV format, the videoinput signals comprise the R, G and B signals, while the sync inputsignals comprise the H and V sync signals. In other embodiments, thesync signals may be combined with one or more of the video componentsignals.

In embodiments using video formats in which the sync information iscombined with one or more of the video component signals (e.g. S-Video,Component video, or RGB video with a combined synchronization signal),the sync signals may be detected and extracted from one or more of theinput video component signals and then re-combined with one or more ofthe video components to provide reference signals for signalcompensation as well as providing sync information.

In the RGBHV embodiment of FIG. 4, transmitter 104 comprises horizontaland vertical sync input terminals 431H and 431V, red, green and bluevideo input terminals 401R, 401G and 401B, input amplifiers 410R, 410G,and 410B, back porch clamp (BPC) generator 430, offset correctioncircuits 440R, 440G, and 440B, uni-polar pulse converters 450H and 450V,differential output amplifiers 460R, 460G and 460B, and differentialoutput terminals 402R, 402G and 402B. Transmitter 104 may also containlocal output amplifiers for each input signal (not shown) that provide alocal video monitor output signal.

Input amplifiers 410 receive the input video signal from video inputterminals 401, and uni-polar pulse converters 450 receive the sync inputsignals from sync input terminals 431. In one or more embodiments,separate amplifiers are utilized for each video component signal. Forexample, in an embodiment for an RGBHV input signal, three inputamplifiers 410 for the video components (one each for the R, G, and Bcomponents) and two uni-polar pulse converters 450 for the sync signals(one each for the H and V sync signals) are used.

Input amplifiers 410 are used in conjunction with horizontal sync BPCgenerator 430 and offset correction circuits 440 to detect andcompensate for any DC offset in the source video signal. In theembodiment of FIG. 4, offset correction circuits 440 determine the DCoffset for each video component using the back porch clamp signal fromthe BPC generator 430, and the amplified video source signal from inputamplifiers 410. Offset correction circuits 440 apply compensation toeach video component via a feedback loop comprising the respective inputamplifier 410 for that component.

The vertical and horizontal synchronization signals 431H and 431V arecoupled to uni-polar pulse converters 450. Uni-polar pulse converters450 assure that sync signals output by transmitter 104 are always thesame polarity regardless of the polarity of the input. An embodiment ofa uni-polar pulse converter 450 is illustrated in FIG. 5.

In the embodiment of FIG. 5, pulse converter 450 comprises twoexclusive-OR gates (e.g. 510 and 520) that process the received syncinput signal. Initially, the sync input signal 501 (e.g. 431H and 431V)is exclusive-ORed with ground in gate 510 and then the output of gate510 is filtered in low-pass filter 530 (which in one or more embodimentscomprises a resistor and capacitor circuit) and exclusive-ORed withitself (i.e. unfiltered output of gate 510) in gate 520 to generate thepolarity-corrected sync output signal 502.

In one or more embodiments, the standardized horizontal sync signal(identified as “H_(SYNCP)” in FIG. 4) is used as both the horizontalsync signal and as the reference pulse signal. In these embodiments,H_(SYNCP) is injected into each of the video signal componentssimultaneously. In addition, the vertical sync signal (“V_(SYNCP)” inFIG. 4) is added to one of the video components to convey the verticalsync information to the receiver.

In the embodiment of FIG. 4, the red video component signal is used toconvey the vertical sync information. H_(SYNCP) is summed with V_(SYNCP)at node 452 and subtracted from the red video component signal (added tothe negative input terminal) at differential amplifier 460R. H_(SYNCP)is subtracted from the green video component at differential amplifier460G; and H_(SYNCP) is subtracted from the blue video component atdifferential amplifier 460B. In this way, a negative reference pulse issimultaneously added to all three differential video output signals.

Differential output amplifiers 460 receive the reference, sync (ifapplicable) and video signals and provide corresponding amplifieddifferential driver signals to differential output terminals 402. In oneor more embodiments, differential output terminals 402 comprise a femaleRJ-45 connector using pin assignments such as those shown in FIG. 2(pins 3 and 6 may be used for transmission of power, digital signals,and/or audio signals). Differential output terminals 402 may beconnected via twisted pair cable 106 of FIG. 1 to receiver 108.

Receiver 108 receives the differential video signals from transmitter104 via twisted pair cable 106. Receiver 108 processes the differentialvideo signals to compensate for insertion loss (and, in one or moreembodiments, for skew) and outputs the compensated video signals to adestination device such as projector 110. FIG. 6 is a block diagram ofan embodiment of receiver 108.

In the embodiment of FIG. 6, Receiver 108 comprises variable gainamplifiers 610R, 610G and 610B, discrete gain amplifiers 620R, 620G and620B, skew adjustment circuit 630; output stages 640R, 640G and 640B, DCoffset compensation circuits 622R, 622B and 622G, and sync detectors650H and 650V. Receiver 108 may also include differential outputterminals (not shown) that output a buffered and/or amplified version ofthe input signals for daisy chaining to other receivers.

The differential video input signals 601 (e.g. 601R, 601G and 601B) arecoupled to the respective variable gain amplifiers 610 and discrete gainamplifiers 620. Each variable gain amplifier 610 works together with thecorresponding discrete gain amplifier 620 to compensate a respective oneof the differential input video signals for insertion losses resultingfrom communication of the signal from transmitter 104 to receiver 108over twisted pair cable 106. In one or more embodiments, each variablegain amplifier 610 is capable of providing a controllable, variableamount of gain over a range from zero (0) to a maximum value (K), andeach discrete gain amplifier 620 provides amplification in controllable,discrete multiples of K (e.g. 0K, 1K, 2K, etc). Together, variable gainamplifiers 610 and discrete gain amplifiers 620 provide controllableamounts of variable gain over an amplification range equal to the sum ofthe maximum gain of variable gain amplifiers 610 and the maximum gain ofdiscrete gain amplifiers 620. In one or more embodiments, K representsthe amount of gain typically required to compensate for signal lossesover a known length of cable (e.g. 300 feet).

The total amount of gain provided by variable gain amplifiers 610 anddiscrete gain amplifiers 620 may be selected based on the length ofcable 106, or may be automatically controlled. The amount of gainprovided by variable gain amplifiers 610 and discrete gain amplifiers620 may be controlled, for example, using a micro-controller thatdetermines the appropriate amount of gain to be applied based on actualand expected signal strength of the reference signal included in thevideo signals received from transmitter 104, as is described in greaterdetail below.

FIG. 8 shows embodiments of a variable gain amplifier 610 and a discretegain amplifier 620. FIG. 8 shows a variable gain amplifier 610 anddiscrete gain amplifier 620 for a single video signal component, namelythe red color component of an RGB signal (designated R_(x) in FIG. 8).However, it will be understood that in one or more embodiments eachcolor component is provided with its own variable gain amplifier 610 anddiscrete gain amplifier 620, as shown, for example, in FIG. 6.

In the embodiment of FIG. 8, variable gain amplifier 610 providesamplification over an initial amplification range of zero up to amaximum gain (represented herein by the letter “K”). Discrete gainamplifier 620 provides selectable, discrete amounts of gain in multiplesof K. For example, in the embodiment of FIG. 8, discrete gain amplifier620 provides selectable gain in the amounts of 0K, 1K, 2K, 3K or 4K.Together, variable gain amplifier 610 and discrete gain amplifier 620provide continuously variable gain over the range from 0 to 5K.

In the embodiment of FIG. 8, variable gain amplifier 610 includes afixed gain amplifier circuit (FGA) 850, a variable gain amplifiercircuit (VGA) 840, and a compensation circuit 842. VGA 840 and FGA 850are both connected to the differential input signals R_(x)(+ve) 801P andR_(x)(−ve) 801N. FGA 850 converts the differential video input signal toa single ended output with fixed gain. VGA 840 adds a controllableamount of variable (DC & AC Compensation) gain to the differential videoinput signal. The outputs of FGA 850 and VGA 840 are summed at node 843.The resulting summed signal is provided to the input of discrete gainamplifier 620 from node 845.

The amount of gain supplied by VGA 840 is controlled by Fine GainControl Signal 805 supplied, for example, by a microcontroller.Compensator circuit 842 is used to set the desired frequency response ofVGA 840. An embodiment of compensator circuit 842 is illustrated in FIG.9A. The fine gain control of VGA 840 compensates for both DC and ACsignal losses in cable lengths of 0 feet to N feet (e.g. 300 feet).

FIG. 9A shows an embodiment in which compensator circuit 842 isconnected to voltage-controlled amplifier 960. In the embodiment of FIG.9A, compensator circuit 842 is connected to the gain setting inputs ofthe voltage controlled gain amplifier 960. Compensator circuit 842comprises a gain setting resistor 950 and one or more series-connectedresistor/capacitor pairs (i.e. 910, 920, 930, and 940) connected to thegain setting inputs of amplifier 960. Gain setting resistor 950 sets theDC gain compensation for the amplifier, while resistor/capacitor pairs910-940 set the poles (AC gain), thereby shaping the transfer functionof the amplifier circuit. Although four pole-setting resistor/capacitorpairs are used in the embodiment of FIG. 9, a greater or lesser numbermay be used depending on the shape of the transfer function desired. Inone or more embodiments, the values of the resistors and capacitors arechosen such that the frequency response of the amplifier correspondsinversely to the frequency response of the cable over which the videosignals are being transmitted, and such that the overall maximum dB gain(e.g. “K”), when the fine gain control is set to maximum, compensatesfor signal loss expected for a predetermined length of the type of cableused (e.g. 300 feet of CAT5 cable). The value (and frequency response)of “K” may be determined by measurement or may be estimated based on theknown characteristics of the cable, such as, for example, the frequencyresponse of CAT5 cable shown in FIG. 11.

Referring back to FIG. 8, if the maximum gain “K” provided by variablegain amplifier 610 corresponds to the insertion loss exhibited by 300feet of CAT5 cable, then variable gain amplifier 610 can providevariable signal compensation corresponding to 0 to 300 feet of CAT5cable. The amount of gain, between 0 and K (e.g. for between 0 and 300foot lengths of CAT5 cable) provided by variable gain amplifier 610 iscontrolled by fine gain control signal 805 (described in greater detailbelow). For longer lengths of cable, additional signal amplification isrequired. In the embodiment of FIG. 8, that additional signalamplification is provided by discrete gain amplifier 620.

Discrete gain amplifier 620 provides additional compensation for longerline lengths in discrete amounts of “K”. For example, for a cable lengthof 450 feet, 1.5K of total compensation is required. In this case,discrete gain amplifier 620 provides 1K (300 feet) of compensation,while variable gain amplifier 610 provides the remaining 0.5K (150 feet)of compensation.

In the embodiment of FIG. 8, discrete gain amplifier 620 comprises amultiplexer 820, a zero-gain buffer 803, and a plurality of fixed gaincompensation circuits 806, 809, 812 and 815. Each compensation circuitprovides a fixed amount of gain (e.g. “K”) that is approximately equalto the maximum amount of gain provided by a variable gain amplifier 610,and that has approximately the same frequency response. FIG. 9B showsthe fixed compensation network encompassed in the fixed gain stages 806,809, 812, and 815 of FIG. 8. The compensation network is placed in thefeedback loop of amplifier 982. The fixed gain compensation networkcomprises a gain setting resistor 980 and one or more series-connectedresistor/capacitor pairs (i.e. 972, 974, 976, and 978) connected inparallel between the inverting input of amplifier 982 and ground. Gainsetting resistor 980 sets the fixed DC gain, while theresistor/capacitor pairs set the poles, thereby shaping the transferfunction of the amplifier circuit for a fixed amount of gaincompensation (e.g. “K”). The compensation circuits are daisy changed,and the output of each successive compensation circuit is connected toone of the inputs of multiplexer 820. In one or more embodiments, theamplifier circuit of FIG. 9B is used for each of the compensationcircuits 806, 809, 812 and 815.

In the embodiment of FIG. 8, input 831 of multiplexer 820 is connectedto the output of buffer 803 (i.e. the buffered output signal fromvariable gain amplifier 610). Input 832 is connected to the output ofcompensation circuit 806 (i.e. the output signal from variable gainamplifier 610 after it has been amplified by compensation circuit 806).Input 833 is connected to the output of compensation circuit 809 (i.e.the output signal from variable gain amplifier 610 after having beenamplified by compensation circuits 806 and 809). Input 834 is connectedto the output of compensation circuit 812 (i.e. the output signal fromvariable gain amplifier 610 after having been amplified by compensationcircuits 806, 809 and 812). Input 835 is connected to the output ofcompensation circuit 815 (i.e. the output signal from variable gainamplifier 610 after having been amplified by compensation circuits 806,809, 812 and 815). If K is the amount of gain provided by eachcompensation circuit, then the additional gain applied to the outputsignal from variable gain amplifier 610 is 0K, 1K, 2K, 3K or 4K,depending on which of inputs 831, 832, 833, 834 or 835 is selected. Ifthe amount of gain supplied by variable gain amplifier 610 is “J” (i.e.a value between 0 and K), the total amount of gain provided by variablegain amplifier 610 and discrete gain amplifier 620 is J, J+K, J+2K, J+3Kor J+4K, depending on which of inputs 831, 832, 833, 834 or 835 isselected.

In the embodiment of FIG. 8, the fixed amount of compensation providedby each of compensation of circuits 806, 809, 812 and 815 isapproximately equal to the maximum compensation provided by variablegain amplifier 610. However, it will be obvious to those of skill in theart that the amount of compensation provided by each of the compensationcircuits 806, 809, 812 and 815 may be greater or less than the maximumprovided by variable gain amplifier 610. Further, the discrete amount ofcompensation provided by each of compensation circuits 806, 809, 812 and815 need not be the same.

The connection of either of inputs 831, 832, 833, 834 or 835 to output802 of multiplexer 820 is controlled by coarse gain selection signal807. In one or more embodiments, coarse gain selection signal 807 isgenerated by a micro-controller, which determines both the coarse gainselection signal 807 and the fine gain control signal 805 based on theactual loss in the reference signal as detected in the video signalreceived from the transmitter as disclosed in co-pending patentapplication Ser. No. 11/309,122, entitled “Method and Apparatus forAutomatic Compensation of Video Signal Losses from Transmission OverConductors,” which is incorporated by reference herein.

If “K” is the amount of compensation corresponding to the losses (in dB)exhibited by 300 feet of CAT5 cable, if maximum compensation provided byvariable gain amplifier 610 is “K”, and if each compensation circuit806, 809, 812 and 815 provides a fixed amount “K” of compensation, thenthe embodiment of FIG. 8 provides variable compensation to compensatefor insertion loss for video transmitted over between zero (0) andfifteen hundred (1500) feet of CAT5 cable.

The amount of gain required to compensate for insertion losses resultingfrom transmission of video signals over long cable lengths will tend toincrease the noise in the video signal. For instance, in the embodimentof FIG. 11, the gain required to compensate for insertion loss for a 40MHz video signal transmitted over 1500 feet of CAT5 cable isapproximately 62 dB, or a voltage gain of approximately 1,259. At suchlarge amplification, the effect of amplified input noise becomessignificant. Noise is not desirable and will show up as sparkles in thevideo display. Noise beyond the video bandwidth can be significantlyreduced with the use of low pass filters. To reduce the noise problem,according to an embodiment of the present invention, multiple stages ofnoise filters are incorporated in discrete gain amplifier stages of anadjustable gain amplifier. FIG. 10 illustrates an embodiment of amulti-stage noise filter of the present invention that may be used withdiscrete gain amplifiers 620 of receiver 108 illustrated in FIGS. 6 and8.

In the embodiment of FIG. 8, each discrete gain amplifier 620 comprisesfour discrete gain amplifier stages 806, 809, 812 and 815. The number ofdiscrete gain amplifier stages applied to a signal at any time dependson the amount of gain required to compensate for insertion losses in theparticular type and length of transmission cable used. The amount ofnoise that is amplified in turn depends upon the total gain supplied.

In the embodiment of FIG. 10, the present invention automaticallyprovides adjustable noise filtering commensurate with the number ofdiscrete gain amplifier stages applied to a signal, R_(x) 1001, byproviding a noise filter in series with one or more discrete gainamplifier stage. As shown in FIG. 10, noise filter 1006 is provided inseries with discrete gain amplifier stage 806, noise filter 1009 isprovided in series with discrete gain amplifier stage 809, noise filter1012 is provided in series with discrete gain amplifier stage 812, andnoise filter 1015 is provided in series with discrete gain amplifierstage 815. Each series-connected discrete amplifier stage/noise filterpair is connected in series to the next pair, with taps between eachpair, before the first pair, and after the last pair each connected toone of the inputs of multiplexer 820. When, as described above, one ofthe inputs of multiplexer 820 is selected (based on the amount of gaindesired) to generate output R_(y) 1002, both the desired number ofdiscrete amplifier stages and the corresponding noise filters areapplied to the video signal being amplified.

Noise filters 1006, 1009, 1012 and 1015 may comprise any type of noisefilter circuits as are known in the art. In one or more embodiments, oneor more of the noise filters are configured to provide a sharp cutoff ofany residual signal components beyond the required video bandwidth,thereby reducing the amount of high-frequency noise in the amplifiedvideo signal. In one or more embodiments, the noise filters areconfigured to attenuate signal components having frequencies aboveapproximately 100 MHz

In one or more embodiments, each noise filter 1006, 1009, 1012 and 1015have identical structure (filter type). In other embodiments, the noisefilters are configured such that the cut off frequency is lowered asmore discrete gain amplifier stages are applied. For example, in oneembodiment, noise filter 1006 may be configured to have a cutofffrequency greater than 100 MHz, noise filter 1009 may be configured tohave a cutoff frequency of approximately 100 MHz, noise filter 1012 maybe configured to have a cutoff frequency of approximately 70 MHz, andnoise filter 1015 may be configured to have a cutoff frequency ofapproximately 50 MHz. Having a higher cutoff frequency for the earlieramplifier stages and a lower cutoff frequency for the later amplifierstages preserves the high frequency components of the video signal forshorter cable lengths (fewer gain stages applied) where the signal tonoise ratio for those components is still acceptable, while providingmore high frequency attenuation for longer cable lengths, where, becauseof the amount of amplification provided, high frequency noise is moresignificant.

One embodiment of a 5-pole elliptical filter used as a noise filter ofthe present invention is illustrated in FIG. 12. In the embodiment ofFIG. 12, the 5-pole elliptical filter comprises inductors L1 and L2 andcapacitors C1, C2, C3, C4, and C5. The 5-pole elliptical filter has asharp cutoff, e.g. >20 dB at the stop frequency (FS) and a stopfrequency to cutoff frequency ratio (i.e. FS/FC) of 1.25, with a maximumof 5% ripple in the pass band. The fixed compensation network poles areadjusted to help compensate for the sin(X)/X component of theirrespective filters. This provides good noise rejection beyond the videobandwidth without significantly affecting the video signal performance.The inductors and capacitors are selected to achieve the desiredfrequency response for the desired noise filter, as is known to those ofskill in the art

Referring back to FIG. 6, after the video components are compensated forinsertion loss, the video signals may be further compensated for skewusing skew adjustment circuit 630, and for DC offset using DC OffsetCompensation circuit 622.

In one or more embodiments, skew adjustment may be accomplished bydetecting the reference signal in each video output component,determining the amount of skew delay among the video signal components,and determining the amount of delay to be applied to each component toeliminate any detected skew. An example skew adjustment circuit isdescribed in co-pending U.S. patent application Ser. No. 11/309,120,entitled “Method And Apparatus For Automatic Compensation Of Skew InVideo Transmitted Over Multiple Conductors”, the specification of whichis incorporated by reference herein.

DC offset compensation may be applied using circuit 622 (i.e. 622B, 622Gor 622R) which comprises a feedback loop around the skew adjustmentcircuit 630 and output amplifiers 640. The DC offset compensationcircuit 622 for each respective color component signal measures thesignal offset (from ground) at the respective output of the video outputamplifiers 640, and generates a corresponding correction signal,accounting for DC offset caused by the receiver's circuitry itself. Inthe embodiment of FIG. 6, each DC offset correction signal feeds backand sums at the respective summing node 624 with the respective gaincompensated video signal component (from the respective discrete gainamplifier 620).

Output signals 602R, 602G and 602B are generated by strippingappropriate reference and/or sync signals from the video signalcomponents by respective output stages 640R, 640G and 640B. In one ormore embodiments, an output stage 640 comprises a switch that groundsthe video output during the sync period. When either the vertical sync(e.g. 603V) or the horizontal sync (e.g. 603H) pulse is high for anyvideo component signal, the video output (i.e. 602) is switched toground; otherwise, the video output is switched to the correspondingvideo signal output of skew adjustment circuit 630. An embodiment of aswitch arrangement that is used in the present invention is illustratedin FIG. 7. In other non-RGBHV video formats the sync signals may not bestripped and/or sync signals may be added to certain video components tore-constitute the video format being transmitted.

In FIG. 7, R_(x) 701 is the video source from the output of skewadjustment circuit 630, and R_(y) 702 is the stripped video output. Thevertical sync strip signal (i.e. V_(Sync)) is OR'd with the horizontalsync strip signal (i.e. H_(Sync)) to generate the “Select” signal ofswitch 710. In one or more embodiments, the vertical and horizontal syncstrip signals are provided to output stages 640 by circuitry thatdetects the sync signals from sync detectors 650H and 650V (shown inFIG. 6). When the Select signal is true (“T”) the video output, R_(y)702, is coupled to ground through switch 710 to remove the sync pulse.Otherwise, i.e. when the Select signal is false (“F”), the video outputR_(y) 702 is coupled to the input signal, R_(x) 701.

In the embodiment of FIG. 6, the sync pulses are detected by comparingthe appropriate color component signal (e.g. the Red (i.e. R_(y))component for the vertical sync signal and the Blue (i.e. B_(y))component for the horizontal sync signal) at the corresponding output ofskew adjustment circuit 630 against appropriate reference voltagelevels. A comparator may be used for such comparison. Thus, in theembodiment of FIG. 6, the vertical sync signal is generated by verticalsync detector 650V when the R_(y) output of skew adjustment circuit 630meets the reference voltage threshold level, V_(REF), and the horizontalsync signal is generated by horizontal sync detector 650H when the B_(y)output of skew adjustment circuit 630 meets the reference voltagethreshold level, H_(REF).

Thus, a novel method and system for providing automatic noise filteringfor video transmitted over conductors has been described. It will beunderstood that the above-described arrangements of apparatus andmethods are merely illustrative of applications of the principles ofthis invention and many other embodiments and modifications may be madewithout departing from the spirit and scope of the invention as definedin the claims. For example, although example embodiments have beendescribed for video signals that comprise three color componentstransmitted over twisted pair conductors, the invention can be used withany type of signal that is transmitted over any number or type ofconductors, as will be understood by those of skill in the art.

1. A method for automatic noise filtering of a signal transmitted overconductors comprising: providing selectable amounts of amplification tosaid signal; and providing selectable amounts of noise filtering to saidamplified signal.
 2. The method of claim 1 wherein said providingselectable amounts of amplification to said signal comprises providingselectable, discrete amounts of amplification to said signal.
 3. Themethod of claim 2 wherein said providing selectable amounts of noisefiltering to said signal comprises providing selectable, discreteamounts of noise filtering to said signal.
 4. The method of claim 3wherein said selectable, discrete amounts of amplification are providedby providing a plurality of daisy-chained discrete gain amplifier stagesthat are selectively applied to the signal.
 5. The method of claim 4wherein said selectable, discrete amounts of noise filtering areprovided by providing a plurality of noise filters with said pluralityof discrete gain amplifier stages.
 6. The method of claim 5 wherein eachof said plurality of discrete gain amplifier stages providesapproximately the same amount of amplification to said signal.
 7. Themethod of claim 5 wherein each of said plurality of noise filtersprovides approximately the same amount of noise filtering to saidsignal.
 8. The method of claim 5 wherein at least two of said noisefilters provide different amounts of noise filtering to said signal. 9.The method of claim 8 wherein a first of said noise filters attenuatessignals above a first cut-off frequency and a second of said noisefilters attenuates signals above a second cut-off frequency.
 10. Themethod of claim 9 wherein said first cut-off frequency is higher thansaid second cut-off frequency.
 11. An apparatus for automatic noisefiltering of a signal transmitted over conductors comprising: a discretegain amplifier that provides selectable amounts of amplification to saidsignal; and a plurality of noise filters that provide selectable amountsof noise filtering to said amplified signal.
 12. The apparatus of claim11 wherein said discrete gain amplifier comprises a plurality ofdiscrete gain amplifier stages.
 13. The apparatus of claim 12 whereinsaid plurality of noise filters comprise a plurality of noise filtercircuits corresponding to said plurality of discrete gain amplifierstages.
 14. The apparatus of claim 13 wherein said plurality of discretegain amplifier stages are daisy-chained such that they may beselectively applied to the signal.
 15. The apparatus of claim 14 whereinsaid a plurality of said noise filter circuits are coupled in serieswith a plurality of said discrete gain amplifier stages.
 16. Theapparatus of claim 15 wherein each of said plurality of discrete gainamplifier stages provides approximately the same amount of amplificationto said signal.
 17. The apparatus of claim 15 wherein each of saidplurality of noise filters provides approximately the same amount ofnoise filtering to said signal.
 18. The apparatus of claim 15 wherein atleast two of said noise filters provide different amounts of noisefiltering to said signal.
 19. The apparatus of claim 18 wherein a firstof said noise filters attenuates signals above a first cut-off frequencyand a second of said noise filters attenuates signals above a secondcut-off frequency.
 20. The apparatus of claim 19 wherein said firstcut-off frequency is higher than said second cut-off frequency.